Fitzgerald & Kingsley's Electric Machinery (IRWIN ELEC&COMPUTER ENGINERING)

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resistors, capacitors, and/or inductors and give the values of the components (we will use these in the next to drive dc machines as well as to provide a controllable dc input to inverters in ac drives. Similarly, techniques for producing stepped and pulse-width-modulated wave- forms of variable amplitudes and frequency are discussed. These techniques are at the heart of variable-speed drive systems which are commonly found in variable-speed ac drives. In general, these losses depend on the metallurgy of the material as well as the flux density and frequency. Information on core loss is typically presented in graphical form. It is plotted in terms of watts per unit weight as a function of flux density; often a family of curves for different frequencies are given. Figure 1.14 shows the core loss Pc for M-5 grain-oriented electrical steel at 60 Hz. To solve for Bm we recognize that for Alnico 5, Bm and Hm are also related by the curve of Fig. 1.16a. Thus this linear relationship, also known as a load line, can be plotted on Fig. 1.16a and the solution obtained graphically, resulting in This chapter will develop some basic tools for the analysis of magnetic field systems and will provide a brief introduction to the properties of practical magnetic materials. In Chapter 2, these results will then be applied to the analysis of transform- ers. In later chapters they will be used in the analysis of rotating machinery.

In general the flux linkage of a coil is equal to the surface integral of the normal component of the magnetic flux density integrated over any surface spanned by that coil. Note that the direction of the induced voltage e is defined by Eq. 1.26 so that if m Topics related to machine control, which were scattered in various chapters in the previous edition, have been consolidated in a single chapter on speed and torque control. In addition, the coverage of this topic has been expanded significantly and now includes field-oriented control of both synchronous and induction machines. which corresponds to a point on the second quadrant of the hysteresis loop. As can be seen from Eq. 1.56, the product of B and H has the dimensions of energy density (joules per cubic meter). We now show that operation of a given permanent-magnet material at this point will result in the smallest volume of that material required to produce a given flux density in an air gap. As a result, choosing a material with the largest available maximum energy product can result in the smallest required magnet volume. chapter introduces the basic concept of electromechanical energy conversion. The fourth chapter then provides an overview of and on introduction to the various machine types. Some instructors choose to omit all or most of the material in Chapter 3 from an introductory course. This can be done without a significant impact to the understanding of much of the material in the remainder of the book.

where 4~ = the flux in the magnetic circuit. Application of Eq. 1.5 to this magnetic circuit yields S o l u t i o n Notice that there are two air gaps in series, of total length 2g, and that by symmetry the flux At any given time, the value of i~ corresponding to the given value of flux can be found directly from the hysteresis loop. For example, at time t t the flux is ~o t and Equation 1.60 is the desired result. It indicates that to achieve a desired flux density in the air gap, the required volume of the magnet can be minimized by operating the magnet at the point of the largest possible value of the B-H product Hm Bm, i.e., the point of maximum energy product. Furthermore, the larger the value of this product, the smaller the size of the magnet required to produce the desired flux density. Hence the maximum energy product is a useful performance measure for a magnetic material, and it is often found as a tabulated "figure of merit" on data sheets for permanent-magnet materials. Here the ~" = Ni is the mmf applied to the magnetic circuit. From Eq. 1.10 we see that a portion of the mmf, .Tc = Hclc, is required to produce magnetic field in the core while the remainder, f g = Hgg, produces magnetic field in the air gap.

material flux density to zero. The significance of remanent magnetization is that it can produce magnetic flux On a more personal note, I would like to express my love for my wife Denise and our children Dalya and Ari and to thank them for putting up with the many hours of my otherwise spare time that this edition required. I promised the kids that I would read the Harry Potter books when work on this edition of Electric Machinery was completed and I had better get to it! In addition, I would like to recognize my life-long friend David Gardner who watched the work on this edition with interest but who did not live to see it completed. A remarkable man, he passed away due to complications from muscular dystrophy just a short while before the final draft was completed. remain in a closed magnetic structure, such as that of Fig. 1.1, made of this material, if the applied mmf (and hence the magnetic field intensity H) were reduced to zero. However, although the M-5 electrical steel also has a large value of remanent magneti- zation (approximately 1.4 T), it has a much smaller value of coercivity (approximately - 6 A/m, smaller by a factor of over 7500). The coercivity Hc corresponds to the value of magnetic field intensity (which is proportional to the mmf) required to reduce the Example 1.9 shows that there is an immense difference between permanent- magnet materials (often referred to as hard magnetic materials) such as Alnico 5 and soft magnetic materials such as M-5 electrical steel. This difference is characterized in large part by the immense difference in their coercivities He. The coercivity can be thought of as a measure of the magnitude of the mmf required to demagnetize the material. As seen from Example 1.9, it is also a measure of the capability of the material to produce flux in a magnetic circuit which includes an air gap. Thus we see that materials which make good permanent magnets are characterized by large values of coercivity He (considerably in excess of 1 kA/m). AC E X C I T A T I O N In ac power systems, the waveforms of voltage and flux closely approximate sinusoidal functions of time. This section describes the excitation characteristics and losses associated with steady-state ac operation of magnetic materials under such operating conditions. We use as our model a closed-core magnetic circuit, i.e., with no air gap, such as that shown in Fig. 1.1 or the transformer of Fig. 2.4. The magnetic path length is lc, and the cross-sectional area is Ac throughout the length of the core. We further assume a sinusoidal variation of the core flux ~o(t); thusEquation 1.45 can be used to calculate the energy input W to the magnetic core of Fig. 1.1 as the material undergoes a single cycle From Eq. 1.1, the relationship between the mmf acting on a magnetic circuit and the magnetic field intensity in that circuit is. 3

We are also considering setting up a section of the website devoted to MATLAB and other numerical analysis packages. For users of MATLAB, the site might contain hints and suggestions for applying MATLAB to Electric Machinery as well as per- haps some Simulink ®3 examples for instructors who wish to introduce simulations into their courses. Similarly, instructors who use packages other than MATLAB might

PROBLEM SOLUTIONS: Chapter 1

The ac excitation characteristics of core materials are often described in terms of rms voltamperes rather than a magnetization curve relating B and H. The theory behind this representation can be explained by combining Eqs. 1.52 and 1.53. Thus, from Eqs. 1.52 and 1.53, the rms voltamperes required to excite the core of Fig. 1.1 to a specified flux density is equal to Finally, instructors may wish to select topics from the control material of Chapter 11 rather than include it all. The material on speed control is essentially a relatively straightforward extension of the material found in earlier chapters on the individ- ual machine types. The material on field-oriented control requires a somewhat more sophisticated understanding and builds upon the dq0 transformation found in Ap- pendix C. It would certainly be reasonable to omit this material in an introductory course and to delay it for a more advanced course where sufficient time is available to devote to it. When an external magnetizing force is applied to this material, the domain mag- netic moments tend to align with the applied magnetic field. As a result, the do- main magnetic moments add to the applied field, producing a much larger value of flux density than would exist due to the magnetizing force alone. Thus the effective permeability lz, equal to the ratio of the total magnetic flux density to the applied magnetic-field intensity, is large compared with the permeability of free space/z0. As the magnetizing force is increased, this behavior continues until all the magnetic moments are aligned with the applied field; at this point they can no longer contribute to increasing the magnetic flux density, and the material is said to be fully saturated. Chapter 11 brings together material that was distributed in various chapters in the previous edition. It is now divided into three main sections: control of dc motors, control of synchronous motors, and control of induction motors. A brief fourth section discusses the control of variable-reluctance motors. Each of these main sections begins with a disCussion of speed control followed by a discussion of torque control. p. cm.--(McGraw-Hill series in electrical engineering. Power and energy) Includes index. ISBN 0-07-366009-4--ISBN 0-07-112193-5 1. Electric machinery. I. Kingsley, Charles, 1904-. II. Umans, Stephen D. III. Title.